- •Radio Engineering for Wireless Communication and Sensor Applications
- •Contents
- •Preface
- •Acknowledgments
- •1 Introduction to Radio Waves and Radio Engineering
- •1.1 Radio Waves as a Part of the Electromagnetic Spectrum
- •1.2 What Is Radio Engineering?
- •1.3 Allocation of Radio Frequencies
- •1.4 History of Radio Engineering from Maxwell to the Present
- •2.2 Fields in Media
- •2.3 Boundary Conditions
- •2.4 Helmholtz Equation and Its Plane Wave Solution
- •2.5 Polarization of a Plane Wave
- •2.6 Reflection and Transmission at a Dielectric Interface
- •2.7 Energy and Power
- •3 Transmission Lines and Waveguides
- •3.1 Basic Equations for Transmission Lines and Waveguides
- •3.2 Transverse Electromagnetic Wave Modes
- •3.3 Transverse Electric and Transverse Magnetic Wave Modes
- •3.4 Rectangular Waveguide
- •3.4.1 TE Wave Modes in Rectangular Waveguide
- •3.4.2 TM Wave Modes in Rectangular Waveguide
- •3.5 Circular Waveguide
- •3.6 Optical Fiber
- •3.7 Coaxial Line
- •3.8 Microstrip Line
- •3.9 Wave and Signal Velocities
- •3.10 Transmission Line Model
- •4 Impedance Matching
- •4.1 Reflection from a Mismatched Load
- •4.2 Smith Chart
- •4.3 Matching Methods
- •4.3.1 Matching with Lumped Reactive Elements
- •4.3.4 Resistive Matching
- •5 Microwave Circuit Theory
- •5.1 Impedance and Admittance Matrices
- •5.2 Scattering Matrices
- •5.3 Signal Flow Graph, Transfer Function, and Gain
- •6.1 Power Dividers and Directional Couplers
- •6.1.1 Power Dividers
- •6.1.2 Coupling and Directivity of a Directional Coupler
- •6.1.3 Scattering Matrix of a Directional Coupler
- •6.1.4 Waveguide Directional Couplers
- •6.1.5 Microstrip Directional Couplers
- •6.2 Ferrite Devices
- •6.2.1 Properties of Ferrite Materials
- •6.2.2 Faraday Rotation
- •6.2.3 Isolators
- •6.2.4 Circulators
- •6.3 Other Passive Components and Devices
- •6.3.1 Terminations
- •6.3.2 Attenuators
- •6.3.3 Phase Shifters
- •6.3.4 Connectors and Adapters
- •7 Resonators and Filters
- •7.1 Resonators
- •7.1.1 Resonance Phenomenon
- •7.1.2 Quality Factor
- •7.1.3 Coupled Resonator
- •7.1.4 Transmission Line Section as a Resonator
- •7.1.5 Cavity Resonators
- •7.1.6 Dielectric Resonators
- •7.2 Filters
- •7.2.1 Insertion Loss Method
- •7.2.2 Design of Microwave Filters
- •7.2.3 Practical Microwave Filters
- •8 Circuits Based on Semiconductor Devices
- •8.1 From Electron Tubes to Semiconductor Devices
- •8.2 Important Semiconductor Devices
- •8.2.1 Diodes
- •8.2.2 Transistors
- •8.3 Oscillators
- •8.4 Amplifiers
- •8.4.2 Effect of Nonlinearities and Design of Power Amplifiers
- •8.4.3 Reflection Amplifiers
- •8.5.1 Mixers
- •8.5.2 Frequency Multipliers
- •8.6 Detectors
- •8.7 Monolithic Microwave Circuits
- •9 Antennas
- •9.1 Fundamental Concepts of Antennas
- •9.2 Calculation of Radiation from Antennas
- •9.3 Radiating Current Element
- •9.4 Dipole and Monopole Antennas
- •9.5 Other Wire Antennas
- •9.6 Radiation from Apertures
- •9.7 Horn Antennas
- •9.8 Reflector Antennas
- •9.9 Other Antennas
- •9.10 Antenna Arrays
- •9.11 Matching of Antennas
- •9.12 Link Between Two Antennas
- •10 Propagation of Radio Waves
- •10.1 Environment and Propagation Mechanisms
- •10.2 Tropospheric Attenuation
- •10.4 LOS Path
- •10.5 Reflection from Ground
- •10.6 Multipath Propagation in Cellular Mobile Radio Systems
- •10.7 Propagation Aided by Scattering: Scatter Link
- •10.8 Propagation via Ionosphere
- •11 Radio System
- •11.1 Transmitters and Receivers
- •11.2 Noise
- •11.2.1 Receiver Noise
- •11.2.2 Antenna Noise Temperature
- •11.3 Modulation and Demodulation of Signals
- •11.3.1 Analog Modulation
- •11.3.2 Digital Modulation
- •11.4 Radio Link Budget
- •12 Applications
- •12.1 Broadcasting
- •12.1.1 Broadcasting in Finland
- •12.1.2 Broadcasting Satellites
- •12.2 Radio Link Systems
- •12.2.1 Terrestrial Radio Links
- •12.2.2 Satellite Radio Links
- •12.3 Wireless Local Area Networks
- •12.4 Mobile Communication
- •12.5 Radionavigation
- •12.5.1 Hyperbolic Radionavigation Systems
- •12.5.2 Satellite Navigation Systems
- •12.5.3 Navigation Systems in Aviation
- •12.6 Radar
- •12.6.1 Pulse Radar
- •12.6.2 Doppler Radar
- •12.6.4 Surveillance and Tracking Radars
- •12.7 Remote Sensing
- •12.7.1 Radiometry
- •12.7.2 Total Power Radiometer and Dicke Radiometer
- •12.8 Radio Astronomy
- •12.8.1 Radio Telescopes and Receivers
- •12.8.2 Antenna Temperature of Radio Sources
- •12.8.3 Radio Sources in the Sky
- •12.9 Sensors for Industrial Applications
- •12.9.1 Transmission Sensors
- •12.9.2 Resonators
- •12.9.3 Reflection Sensors
- •12.9.4 Radar Sensors
- •12.9.5 Radiometer Sensors
- •12.9.6 Imaging Sensors
- •12.10 Power Applications
- •12.11 Medical Applications
- •12.11.1 Thermography
- •12.11.2 Diathermy
- •12.11.3 Hyperthermia
- •12.12 Electronic Warfare
- •List of Acronyms
- •About the Authors
- •Index
56 Radio Engineering for Wireless Communication and Sensor Applications
3.6 Optical Fiber
TE and TM wave modes may propagate, not only in hollow metal waveguides, but also in dielectric waveguides. An optical fiber is actually a dielectric waveguide with a circular cross section, in which total internal reflection confines light in the fiber. Optical fibers are used in many kinds of communication networks, usually at wavelengths of 0.8 to 1.6 mm at infrared. The optical carrier is modulated with data rates up to several gigabits per second.
Optical fibers are made of quartz, glass, or plastic. An optical fiber consists of a core and a cladding. The index of refraction n = √er of the core is larger than that of the cladding. The refractive index of the cladding is adjusted to a proper value by doping quartz with metal oxides as TiO2 , Al2O3 , GeO2 , or P2O3 . Optical fibers can be divided into three types, as shown in Figure 3.11:
1. Single-mode fiber: core radius 1–16 m m, cladding radius 50–100
mm.
2.Multimode fiber with a step in the index of refraction: core radius 25–60 m m, cladding radius 50–150 m m.
3.Multimode fiber with a continuous change in the index of refraction: core radius 10–35 mm, cladding radius 50–80 mm.
Figure 3.11 Structures of optical fibers: (a) a single-mode fiber; (b) a multimode fiber with a step in the refractive index; (c) a multimode fiber with a continuous change in the refractive index.
Transmission Lines and Waveguides |
57 |
An optical cable is usually made of several optical fibers. Steel wires and textile fibers as nylon give strength to the cable and support the fibers. Copper wires carry current for the repeater amplifiers if needed.
The solutions of the longitudinal field components in the core are
Ez = AJn (kr ) cos (nf) |
(3.70) |
Hz = BJn (kr ) sin (nf) |
(3.71) |
The solutions in the cladding are |
|
Ez = CHn ( xr ) cos (nf ) |
(3.72) |
Hz = DHn ( xr ) sin (nf) |
(3.73) |
In these equations, Jn (kr ) is the Bessel function of the first kind of order n ; Hn ( x r ) is the Hankel function of the first kind of order n ; k is the transverse propagation constant in the core; and x is the transverse propagation constant in the cladding. Other field components are solved from these longitudinal fields, as in the case of metal waveguides, except now the boundary conditions are different, that is, the tangential components of E and H are continuous at the boundary of two dielectric materials.
From the expressions of longitudinal fields we can see that only cylindrically symmetric (n = 0) wave modes are either TE or TM wave modes. Other wave modes are hybrid modes, denoted as EH or HE wave modes, for which both electric and magnetic fields have nonzero longitudinal components.
In a multimode fiber the number of propagating wave modes may be very large. The number of modes is approximately [7]
N = |
16 |
(n 21 − n 22 ) a 2 |
(3.74) |
|
|||
|
l20 |
|
where l 0 is the wavelength in free vacuum, n 1 and n 2 are the refractive indices of core and cladding, respectively, and a is the radius of the core.
Example 3.3
Find the number of wave modes at a wavelength of 1.55 m m in a quartz fiber having a core radius of 40 mm. The refractive index of the cladding is 1% lower than that of the core.
58 Radio Engineering for Wireless Communication and Sensor Applications
Solution
The dielectric constant of quartz is er = 3.8. Hence n 1 = √ |
3.8 |
= 1.95 and |
|
n 2 |
= 0.99 × 1.95 = 1.93. From (3.74) we obtain the number of wave modes, |
||
N |
= 800. |
|
|
The loss mechanisms of an optical fiber are:
•Dielectric absorption loss;
•Scattering loss due to the imperfections of the fiber;
•Radiation loss due to the bending of the fiber.
Properties making the optical fiber an excellent transmission medium for many applications are
•Small size and weight;
•Low attenuation—only 0.2 dB/km at 1.55 mm—allowing cables hundreds of kilometers long without any repeater amplifiers;
•Immunity to interference and difficulty of interception;
•Reliability;
•Broad bandwidth;
•Low price compared to copper cable.
3.7Coaxial Line
A coaxial line consists of two concentric conductors with circular cross sections and insulating material between them, as shown in Figure 3.12.
Figure 3.12 Cross section of a coaxial line.
Transmission Lines and Waveguides |
59 |
The inner radius of the outer conductor is ro and the radius of the inner conductor is r i ; the relative permittivity of the insulator is er . The fields are confined to the space between the conductors.
The fields of the TEM wave mode of the coaxial line can be derived from Laplace’s equation (3.21) using the scalar potential F(r , f ). In the cylindrical coordinate system, Laplace’s equation is written as
1 ∂ |
∂F(r , f) |
|
1 ∂2F(r , f ) |
|
|
||||
|
|
|
Sr |
∂r |
D + |
|
∂f 2 |
= 0 |
(3.75) |
r |
∂r |
r 2 |
Applying the boundary conditions F(ro , f ) = 0 and F(r i , f) = V, the potential is solved to be
F(r , f ) = V |
ln (ro /r ) |
(3.76) |
ln (ro /r i ) |
The electric field is the negative gradient of the potential:
E(r , f ) = −=F(r , f) = ur |
V |
|
|
1 |
(3.77) |
||
|
|
|
|
|
|||
ln (ro |
/r i ) r |
||||||
|
|
where ur is the unit vector in the radial direction. This is also the electric field of a cylindrical capacitor. The magnetic field of the coaxial line is
H(r , f ) = |
1 |
uz × E(r , f) = uf |
V |
|
= uf |
I |
(3.78) |
|
h |
hr ln (ro /ri ) |
2pr |
||||||
|
|
|
|
where h = √m/e is the wave impedance, I is the current in the inner conductor, and uf is the unit vector perpendicular to the radial direction. A current I flows also in the outer conductor but to the opposite direction.
The characteristic impedance of the coaxial line is
Z 0 |
= |
V |
= |
h |
ln (ro /r i ) |
(3.79) |
|
|
I |
2p |
|||||
|
|
|
|
|
|
The 50-V characteristic impedance has become a standard value. Most measurement instruments and thus also most devices have 50-V input and output connectors.
The attenuation constant due to conductor loss is
60 Radio Engineering for Wireless Communication and Sensor Applications
a c = |
R s |
|
|
1 |
+ |
1 |
|
(3.80) |
|
4p Z 0 |
Sro |
r i D |
|||||||
|
|
|
For an air-filled coaxial line with a given outer conductor dimension, the minimum of the attenuation constant is obtained when the characteristic impedance is Z 0 = 77V. The attenuation constant due to dielectric loss is
a d = |
p |
tan d |
(3.81) |
|
|||
|
l |
|
Also TE and TM wave modes may propagate in a coaxial line, if the operating frequency is larger than the cutoff frequency of these wave modes. To avoid losses and unanticipated phenomena due to these modes, the operating frequency should be chosen to be low enough. An approximate rule is that the circumference corresponding to the average radius should be smaller than the operating wavelength:
l > p (ro + r i ) |
(3.82) |
Consequently, the coaxial lines used at high frequencies should be thin enough to make sure that only the TEM wave mode may propagate.
Example 3.4
Show that the attenuation constant of an air-filled coaxial line having a fixed diameter is at minimum when the characteristic impedance is Z 0 = 77V.
Solution
According to (3.79) and (3.80) the attenuation constant is proportional to the quantity
r1o S1 + rroi Dln (r1o /r i )
Now ro is constant. Let us denote ro /r i = x and derivate with respect of x :
|
1 1 + x |
1 |
|
ln x − (1 + x ) (1/x ) |
||||
D F |
|
|
|
G = |
|
|
|
|
ro |
ln x |
ro |
|
ln2 x |
|
By setting this derivative equal to zero, we obtain