диафрагмированные волноводные фильтры / 7ac4e4af-063a-4ed2-b8d5-43cf78ede2ce
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4 - Channel |
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Contiguous MUX |
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Superimposed |
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Channel Rejections |
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After First |
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Optimization of Filter |
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Parameters |
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Rejection |
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12,450 |
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Frequency (MHz)
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(a) |
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(dB) |
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4 - Channel |
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Contiguous MUX - |
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Loss |
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Common Port |
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Return Loss |
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Return |
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After First |
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20 |
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Optimization of Filter |
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Parameters |
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Port |
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Common |
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12,450 |
12,500 |
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12,700 |
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Frequency (MHz)
(b)
Figure 18. Four-channel manifold multiplexer after first optimization of filter parameters:
(a) superimposed channel transfer characteristics and (b) CPRL.
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(dB) |
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4 - Channel |
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Contiguous MUX - |
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Common Port |
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Loss |
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Return Loss |
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Final Optimized |
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Return |
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Solution |
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Port |
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Common |
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12,450 |
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Frequency (MHz)
Figure 19. Four-channel manifold multiplexer: final performance of CPRL.
Demonstration
of the Piecewise Optimization Process
The piecewise optimization process will be demonstrated through the optimization of a four-contigous-channel Ku-band waveguide manifold multiplexer. The channel electrical specifications for this particular case were satisfied with 5-2 quasielliptic filters with 30-dB rejection lobe levels and DBWs of 38-MHz and 40MHz center frequency spacings, which falls within the definition of contiguity.
Designing the filters as singly terminated prototypes and attaching them to the manifold with the initial manifold spacings and stub lengths gives a poor performance, as shown in Figure 16. The CPRL is poor and one of the channels is unrecognizable.
Figure 17 shows the dramatic improvement that results from the optimization of the along-manifold lengths. Now the channel rejection characteristics are close to design, and the average CPRL is on the order of 10 dB.
Further improvement in CPRL is obtained after first optimization of the stub lengths and the first four parameters (first coupling iris MS1 , first cavity tuning state M11 , second coupling M12 , second cavity tuning state M22) of each filter. The computed response following this procedure is described in Figure 18. The inner rejection lobe levels are close to the design of 30 dB, but the outer lobe levels—because there are no neighbors on the outer side of the group—have dropped to about 24 dB. The effect of not having a
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contiguous neighbor on one side is evident in the |
The main advantage of the hybrid- |
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rejection responses of channels 1 and 4—the lobe lev- |
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coupled approach is its directional |
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els and rejection slopes on the outer sides are not as |
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steep as the sides with a contiguous neighbor. This |
property, which minimizes the |
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causes a small amount of asymmetric in-band distor- |
interaction between the channel filters. |
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tion to group delay and insertion loss as well. |
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Then the refinement of return loss optimization cycles |
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is carried out, and the final result is |
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shown in Figure 19. Now the CPRL |
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is above 23 dB over all the channel |
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20 Channel COMUX |
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bandwidths. The simulations have |
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all been made assuming a Qu factor |
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of 12,000, but the optimizations were |
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carried out with a lossless network |
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to speed |
up the process. Using a |
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moderate-speed PC (700 MHz), the |
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ILs |
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entire optimization process took |
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and |
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about 2 min. |
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RL |
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This |
optimization |
strategy |
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appears to work well even for larg- |
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er numbers of channels. Figure 20 |
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shows the CPRL and rejection char- |
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acteristics of a manifold multiplexer |
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with 20 contiguous channels at C- |
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Frequency (MHz) |
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band (fourth-degree filters) [21], |
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which was designed using the |
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Figure 20. 20-channel manifold multiplexer: superimposed channel transfer charac- |
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piecewise |
optimization |
process. |
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teristics and CPRL. |
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This multiplexer has on the order of |
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300 frequency sampling points and |
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220 electrical elements of |
varying |
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Tuning Screw
sensitivities and different constraints that all need to be correctly valued before the overall multiplexer will operate to specification.
Further Optimization
Using EM Techniques
Optimization techniques for multiplexer design have been developed to a high degree of sophistication now, and worthy of note here is the space mapping technique [23], which involves optimizing a coarse model [circuit or hybrid circuit model with embedded electromagnetic (EM)-modeled components] and a fine model (e.g., full-wave electromagnetic modeling). Because of the large number of optimization variables, the fine-model EM simulator takes a formidable amount of computer CPU time and has to be used sparingly during the optimization process. On the other hand, the coarse simulator can analyze the circuit very rapidly, especially if the S-parameters of fixed
Input |
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Waveguide |
Cavity 1 |
Cavity 4 |
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Cavity 2 |
Cavity 3 |
Rod Coupling for M23
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Output |
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Waveguide |
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Cavity 5 |
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Figure 21. Fifth-degree DR filter structure: (a) side view and (b) top view.
October 2007 |
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A direction filter is a four-port device in which one port is terminated in
a load.
and noninteracting elements (e.g., the manifold waveguide junctions) are modeled in advance by EM techniques and are available to the main program either as look-up tables or with the call of a rapid specialist routine. It, therefore, provides a means to simulate the manifold multiplexer with a good degree of accuracy and efficiency.
To illustrate the complete multiplexer design procedure including EM optimization, we consider a 10channel manifold-coupled output multiplexer in the frequency band of 3.5-4.25 GHz. Eight channels have a bandwidth of 1.5%, and the remaining two have a bandwidth of 0.8%. Every channel is a fifth-degree dielectric resonator (DR) filter as shown in Figure 21.
Ansoft HFSS is used as a fine model of every channel and the network model is used as a coarse model.
Ideal channel coupling values are obtained in the first step of the design procedure in the preceding sections. Space-mapping optimization [23] is then applied to each channel to get the optimal channel dimensions. For example, the results of applying space-mapping optimization to the first channel are shown in Figure 22 (seven iterations are required). An accurate multiplexer model is obtained by replacing each channel with the corresponding S-parameter sweep obtained by HFSS at the optimal channel dimensions. As a result, the new multiplexer model includes channel dispersion and spurious modes. Finally, the manifold parameters are reoptimized to meet the required specifications. Figure 23 compares the multiplexer ideal response and the EM response, where every channel is replaced by its simulated S-parameters (by Ansoft HFSS). The measured response of the multiplexer is shown in Figure 24. The spurious modes predicted by
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Frequency (GHz) |
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Figure 22. Responses of the first channel of the 10-channel DR output multiplexer (solid line is the ideal response and dotted line is the EM response at the optimal design parameters); |S21| and |S11| in dB.
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Frequency (GHz)
Figure 23. The ideal response of the 10-channel DR multiplexer prototype (solid line) versus the EM response (dotted line).
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Frequency (GHz)
Figure 24. Measured response of the 10-channel DR multiplexer.
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EM analysis in Figure 23 correlate very well with the measurements in Figure 24. Finally, a fully integrated multiplexer assembly is shown in Figure 25 together with input and output circuitry.
Conclusions
Following a brief review of different types of multiplexer configurations, a systematic design approach has been outlined for the design of manifold-coupled multiplexers. The piecewise approach, optimizing parts of the multiplexer separately in repeated cycles while converging upon an optimal solution, has proved to be very effective for most practical applications. The technique is readily applicable to manifold multiplexers incorporating an arbitrary number of channels, regardless of their bandwidths and channel separations. There are no restrictions on the design and implementation of channel filters onto the manifold; they may be asymmetric, and may incorporate transmission zeros, group delay equalization zeros, or both. The manifold itself is a transmission line, be it a coaxial line or a rectangular waveguide or some other low-loss structure. The costly EM simulation is used economically on manifold junctions and channel filters through the use of space-mapping optimization techniques, where EMbased simulators are used to fine-model each multiplexer channel and coupling matrix representation is used to coarse-model the performance. Fine details such as tuning screws may be included in the design process. This design procedure takes into account the effects of dispersion and spurious modes and, as a result, the overall design and final tuning time can be significantly reduced.
Acknowledgement
The authors would like to thank Prof. Raafat Mansour for providing part of the material in the “Multiplexer Configurations” section.
References
[1]J. Uher, J. Bornemann, and U. Rosenberg, Waveguide Components for Antenna Feed Systems—Theory and CAD. Norwood, MA: Artech House, 1993.
[2]G. Matthaei, L. Young, and M.T. Jones, Microwave Filters, Impedance Matching Networks and Coupling Structures. Norwood, MA: Artech House, 1985.
[3]E.G. Cristal and G.L. Matthaei, “A technique for the design of multiplexers having contiguous channels,” IEEE Trans. Microwave Theory Tech., vol. MTT-10, pp. 88–93, Jan. 1964.
[4]A.E. Atia, “Computer aided design of waveguide multiplexers,”
IEEE Trans. Microwave Theory Tech., vol. MTT-22, pp. 322–336, Mar. 1974.
[5]M.H. Chen, F. Assal, and C. Mahle, “A contiguous band multiplexer,” Comsat Tech. Rev., vol. 6, pp. 285–307, Fall 1976.
[6]C.M. Kudsia, J. Dorey, j. Heierli, K.R. Ainsworth, G.L.P. Lo, “A new type of low loss 14 GHz high power combining network,” in Proc. 9th Eur. Microwave Conf., England, Oct. 1979, pp. 386–391.
[7]C.M. Kudsia, K.R. Ainsworth, and M.V. O’Donovan, “Microwave filters and multiplexing networks for communication satellites in
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Figure 25. A fully integrated C-band 10-channel multiplexer assembly with DR filters.
the 1980s,” in Proc. AIAA 8th Communications Satellite Systems Conf., Apr. 1980.
[8]J.D. Rhodes and R. Levy, “Design of general manifold multiplexers,” IEEE Trans. Microwave Theory Tech., vol. 27, no. 2, pp. 111–123, Feb. 1979.
[9]J.D. Rhodes and R. Levy, “A generalized multiplexer theory,” IEEE Trans. Microwave Theory Tech., vol. 27, no. 2, pp. 99–111, Feb. 1979.
[10]D. Doust, et al., Satellite multiplexing using dielectric resonator filters,” Microwave J., vol. 32, no. 12, pp. 93–166, Dec. 1989.
[11]J. Bandler, S. Daijavad, and Q.-J. Zhang, “Exact simulation and sensitivity analysis of multiplexing networks,” IEEE Trans. Microwave Theory Tech., vol. MTT-34, pp. 111–102, Jan. 1986.
[12]D.S. Levinson and R.L. Bennett, “Multiplexing with high performance directional filters,” Microwave J., pp. 92–112, Jun. 1989.
[13]D. Rosowsky, “Design of manifold multiplexers,” in Proc. ESA Workshop on Microwave Filters, Jun. 1990, pp. 145–156 .
[14]U. Rosenberg, D. Wolk, and H. Zeh, “High performance output multiplexers for Ku-band satellites,” in Proc. 13th AIAA International Communication Satellite Conf., Los Angeles, Mar. 1990, pp. 747–752.
[15]C. Kudsia, R. Cameron, and W.C. Tang, “Innovation in microwave filters and multiplexing networks for communication satellite systems,” IEEE Trans. Microwave Theory Tech., vol. MTT-40,
pp.1133–1149, Jun. 1992.
[16]M. Guglielmi, “Simple CAD procedures for microwave filters and multiplexers,” IEEE Trans. Microwave Theory Tech., vol. MTT-42,
pp.1347–1352, Jul. 1994.
[17]R.R. Mansour, S. Ye, V. Dokas, B. Jolley, W.C. Tang, and C. Kudsia, “System integration issues of high power HTS output multiplexers,” IEEE Trans. Microwave Theory Tech., vol. MTT-48,
pp.1199–1208, Jul. 2000.
[18]M.H. Chen, “Singly-terminated pseudo-elliptic function filter,” Comsat Technical Rev., vol. 7, pp. 527–541, Fall 1977.
[19]S. Lundquist, M. Mississian, M. Yu, and D. Smith, “Application of high power output multiplexers for communications satellites,” in Proc. 19th AIAA Int. Communication Satellite System Conf. and Exhibit, pp. 12–15, May 2001.
[20]S. Lundquist, M. Yu, D.J. Smith, and W. Fitzpatrick, “KU-band temperature compensated high power multiplexers,” in Proc. 20th AIAA Int. Commun. Satellite Syst. Conf. and Exhibit, May 12–15, 2002.
[21]M. Yu, “Design of multiplexers with many channels,” in Proc. IEEE International Microwave Symp., San Francisco, Jun. 2006.
[22]M. Yu, “EM based `smart’ design techniques for filters and multiplexers,” in Proc. IEEE Int. Microwave Symp., Fort Worth, Texas, Jun. 6–11, 2004.
[23]M.A. Ismail, D. Smith, A. Panariello, Y. Wang, and M. Yu, “EM based design of large-scale dielectric resonator filters and multiplexers by space mapping,” IEEE Trans. Microwave Theory Tech. (Special Issue on Electromagnetics-Based Optimization of
Microwave Components and Circuits), vol. 52, no. 1, pp. 386–392, Jan. 2004.
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